High voltage resistive output stage circuit

ABSTRACT

Some embodiments include a high voltage, high frequency switching circuit. The switching circuit may include a high voltage switching power supply that produces pulses having a voltage greater than 1 kV and with frequencies greater than 10 kHz and an output. The switching circuit may also include a resistive output stage electrically coupled in parallel with the output and between the output stage and the high voltage switching power supply, the resistive output stage comprising at least one resistor that discharges a load coupled with the output. In some embodiments, the resistive output stage may be configured to discharge over about 1 kilowatt of average power during each pulse cycle. In some embodiments, the output can produce a high voltage pulse having a voltage greater than 1 kV and with frequencies greater than 10 kHz with a pulse fall time less than about 400 ns.

BACKGROUND

Producing high voltage pulses with fast rise times and/or fast falltimes is challenging. For instance, to achieve a fast rise time and/or afast fall time (e.g., less than about 50 ns) for a high voltage pulse(e.g., greater than about 5 kV), the slope of the pulse rise and/or fallmust be incredibly steep (e.g., greater than 10⁻¹¹ V/s). Such steep risetimes and/or fall times are very difficult to produce especially incircuits driving a load with low capacitance. Such pulse may beespecially difficult to produce using standard electrical components ina compact manner; and/or with pulses having variable pulse widths,voltages, and repetition rates; and/or within applications havingcapacitive loads such as, for example, a plasma.

SUMMARY

Some embodiments include a high voltage, high frequency switchingcircuit. The switching circuit may include a high voltage switchingpower supply that produces pulses having a voltage greater than 1 kV andwith frequencies greater than 10 kHz and an output. The switchingcircuit may also include a resistive output stage electrically coupledin parallel with the output and between the output stage and the highvoltage switching power supply, the resistive output stage comprising atleast one resistor that discharges a load coupled with the output. Insome embodiments, the resistive output stage may be configured todischarge over about 1 kilowatt of average power during each pulsecycle. In some embodiments, the output can produce a high voltage pulsehaving a voltage greater than 1 kV and with frequencies greater than 10kHz with a pulse fall time less than about 400 ns.

In some embodiments, the high voltage switching power supply maycomprise a power supply, at least one switch, and a step-up transformer.

In some embodiments, the resistive output stage may comprise aninductor.

In some embodiments, the resistance of the resistor in the resistiveoutput stage may be less than 200 ohms.

In some embodiments, the resistor may comprise a plurality of resistorsarranged in series or parallel having a combined capacitance less thanabout 200 pF.

In some embodiments, the resistive output stage includes an inductor anda resistor, and wherein the inductance L of the inductor and theresistance R of the resistor are set to satisfy L/R≈tp, where tp is thepulse width of the pulse.

In some embodiments, the resistor in the resistive output stage has aresistance R and the output is coupled with a load having a capacitanceC such that R≈C/tf where tf is the pulse fall time.

In some embodiments, the resistor in the resistive output stage includeshas a resistance R and the output is coupled with a load having acapacitance C such that R≈C/tr where tr is the pulse rise time.

In some embodiments, the resistive output stage includes a blockingdiode.

In some embodiments, the output produces a high-voltage, negative biasvoltage within a plasma when the high voltage switching power supply isnot providing a high voltage pulse.

In some embodiments, the output can produce a high voltage pulse havinga voltage greater than 1 kV and with frequencies greater than 10 kHzwith a pulse fall time less than about 250 ns.

In some embodiments, the high voltage, high frequency switching circuitmay be coupled with a load that is capacitive in nature with acapacitance less than 50 nF, wherein the load capacitance does not holdcharges for times greater than 10 μs.

In some embodiments, the high voltage, high frequency switching circuitmay be coupled with a load that is capacitive in nature and the highvoltage, high frequency switching circuit rapidly charges the loadcapacitance and discharges the load capacitance

Some embodiments may include high voltage, high frequency switchingcircuit that includes a high voltage switching power supply thatproduces pulses having a voltage greater than 1 kV and with frequenciesgreater than 10 kHz; an output; and a resistive output stageelectrically coupled to, and in parallel with the output of the highvoltage switching power supply, the resistive output stage comprising atleast one resistor.

In some embodiments, the output can produce a high voltage pulse havinga voltage greater than 1 kV with frequencies greater than 10 kHz andwith pulse fall times less than about 400 ns, and wherein the output iselectrically coupled to a plasma type load.

In some embodiments, the plasma type load can be modeled as havingcapacitive elements less than 20 nF in size.

In some embodiments, a potential is established to accelerate ions intoa surface through the action of the high voltage high frequencyswitching power supply

In some embodiments, the plasma type is largely capacitive in nature.

In some embodiments, the plasma type load includes a dielectric barrierdischarge.

In some embodiments, the high voltage high frequency switching powersupply delivers peak powers greater than 100 kW.

In some embodiments, the high voltage switching power supply comprises apower supply, at least one switch, and a step-up transformer.

These illustrative embodiments are mentioned not to limit or define thedisclosure, but to provide examples to aid understanding thereof.Additional embodiments are discussed in the Detailed Description, andfurther description is provided there. Advantages offered by one or moreof the various embodiments may be further understood by examining thisspecification or by practicing one or more embodiments presented.

A pulse generator is disclosed that includes one or more of thefollowing stages a driver stage, a transformer stage, a rectifier stage,and an output stage. The driver stage may include at least one of one ormore solid state switches such as, for example, an insulated gatebipolar transistor (IGBT) or a metal-oxide-semiconductor field-effecttransistor (MOSFET). The driver stage may also have a stray inductanceless than 1,000 nH. The transformer stage may be coupled with the driverstage such as, for example, through a balance stage and may include oneor more transformers. The rectifier stage may be coupled with thetransformer stage and may have a stray inductance less than 1,000 nH.The output stage may be coupled with the rectifier stage. The outputstage may output a signal pulse with a voltage greater than 2 kilovoltsand a frequency greater than 5 kHz. In some embodiments, the outputstage may be galvanically isolated from a reference potential.

A method is also disclosed that includes the following: generating afirst input waveform having a first input frequency, a first inputvoltage, and a first input duration; outputting a first output pulsehaving a rise time less than 1,000 nanoseconds, a first output voltagegreater than the first input voltage, and a pulse width substantiallyequal to the first input duration; turning off the first input waveformfor a second input duration; generating a second input waveform having asecond input frequency, a second input voltage, and a second inputduration, wherein the second input duration is different than the firstinput duration; and outputting a second output pulse having a rise timeless than 1,000 nanoseconds, a second output voltage greater than thesecond input voltage, and a pulse width substantially equal to thesecond input duration.

BRIEF DESCRIPTION OF THE FIGURES

These and other features, aspects, and advantages of the presentdisclosure are better understood when the following Detailed Descriptionis read with reference to the accompanying drawings.

FIG. 1 is an example circuit that can be used to control the voltage ona load according to some embodiments.

FIG. 2 is an example circuit that can be used to control the voltage ona load according to some embodiments.

FIG. 3 is an example circuit that can be used to control the voltage ona load according to some embodiments.

FIG. 4 is an example circuit with a resistive output stage according tosome embodiments.

FIG. 5 is an example circuit with a resistive output stage according tosome embodiments.

FIG. 6 is an example circuit representation of a circuit used to set theion energy in a plasma according to some embodiments.

FIG. 7 is a single switch configuration that may be used instead of thetwo-switch configuration, to set the ion energy in a plasma, accordingto some embodiments.

FIG. 8 shows some example waveforms of the voltage and current within ahigh voltage switching application according to some embodiments.

FIG. 9 is a circuit diagram of a circuit with a resistive output stageaccording to some embodiments.

FIG. 10 is an example circuit with a resistive output stage according tosome embodiments.

FIG. 11 is an example circuit with a resistive output stage according tosome embodiments.

FIG. 12 is an example circuit with a resistive output stage according tosome embodiments.

FIG. 13 is an example circuit with a resistive output stage according tosome embodiments.

FIG. 14 is an example block diagram of a pulse generator according tosome embodiments.

FIG. 15A is an example driver stage according to some embodimentsdescribed in this document.

FIG. 15B is an example balance stage according to some embodimentsdescribed in this document.

FIG. 15C is an example balance stage according to some embodimentsdescribed in this document.

FIG. 15D is an example balance stage according to some embodimentsdescribed in this document.

FIG. 15E is an example transformer stage according to some embodimentsdescribed in this document.

FIG. 15F is an example rectifier stage according to some embodimentsdescribed in this document.

FIG. 16A is an example filter stage according to some embodimentsdescribed in this document.

FIG. 16B is an example filter stage according to some embodimentsdescribed in this document.

FIG. 16C is an example filter stage according to some embodimentsdescribed in this document.

FIG. 16D is an example sink stage according to some embodimentsdescribed in this document.

FIG. 17 is an example circuit diagram that may comprise all or part of apulse generator according to some embodiments described in thisdocument.

FIGS. 18A, 18B and 18C are example graphs of an output pulse accordingto some embodiments described in this document.

FIG. 19 is an example pulse generator according to some embodimentsdescribed in this document.

FIG. 20A is an example circuit diagram of a portion of a pulse generatoraccording to some embodiments described in this document.

FIG. 20B is an example of an output waveform produced from the pulsegenerator shown in FIG. 20A.

FIG. 21A is an example circuit diagram of a portion of a pulse generatoraccording to some embodiments described in this document.

FIG. 21B is an example of an output waveform produced from the pulsegenerator shown in FIG. 21A.

FIG. 22A is an example circuit diagram of a portion of a pulse generatoraccording to some embodiments described in this document.

FIG. 22B is an example of an output waveform produced from the pulsegenerator shown in FIG. 22A.

FIG. 22C is another example of an output waveform produced from thepulse generator shown in FIG. 22A.

FIG. 23A is an example circuit diagram of a portion of a pulse generatoraccording to some embodiments described in this document.

FIG. 23B is an example of an output waveform produced from the pulsegenerator shown in FIG. 23A compared with the input waveform.

FIG. 23C is an example of an output waveform produced from the pulsegenerator shown in FIG. 23A compared with the input waveform.

FIG. 24A is an example circuit diagram of a portion of a pulse generatoraccording to some embodiments described in this document.

FIG. 24B is an example of an output waveform produced from the pulsegenerator shown in FIG. 24A compared with the input waveform.

FIG. 24C is an example of an output waveform produced from the pulsegenerator shown in FIG. 24A compared with the input waveform.

FIG. 25A is an example circuit diagram 1200 of a portion pulse generatoraccording to some embodiments described in this document.

FIG. 25B is an example of an output waveform produced from the pulsegenerator shown in FIG. 25A compared with the output waveform producedfrom the pulse generator shown in FIG. 24A.

FIG. 26A is an example circuit diagram of a portion of a pulse generatoraccording to some embodiments described in this document.

FIG. 26B is an example of an output waveform produced from the pulsegenerator shown in FIG. 26A.

FIG. 27A is an example circuit diagram of a portion of a pulse generatoraccording to some embodiments described in this document.

FIG. 27B is an example of an output waveform produced from the pulsegenerator shown in FIG. 27A.

FIG. 28 is a flowchart of a process for producing an arbitrary pulsewidth output signal according to some embodiments described in thisdocument.

DETAILED DESCRIPTION

In some embodiments, a resistive output stage is a collection of circuitelements that can be used to control the shape of a voltage waveform ona load. In some embodiments, a resistive output stage may includepassive elements only (e.g., resistors, capacitors, inductors, etc.);and in other embodiments a resistive output stage may include activecircuit elements (e.g., switches) as well as passive circuit elements.In some embodiments, a resistive output stage, for example, can be usedto control the voltage rise time of a waveform and/or the voltage falltime of waveform. In the associated figures, examples of resistiveoutput stages are shown and are represented by different symbols such asR, Zp, ZL, ZC, etc. These are examples and should not be viewed as tolimit the varieties of resistive output stages covered in the variousembodiments described in this document.

In some embodiments, a resistive output stage can discharge capacitiveloads. For example, these capacitive loads may have small capacitance(e.g., about 10 pF, 100 pF, 500 pF, 1 nF, 10 nF, 100 nF, etc.). Asanother example, a rapid discharge is a pulse having a fall time that isshorter than about 1 ns, 10 ns, 50 ns, 100 ns, 250 ns, 500 ns, 1,000 ns,etc.

In some embodiments, a resistive output stage can be used in circuitswith pulses having a high pulse voltage (e.g., voltages greater than 1kV, 10 kV, 20 kV, 50 kV, 100 kV, etc.), high frequencies (e.g.,frequencies greater than 1 kHz, 10 kHz, 100 kHz, 200 kHz, 500 kHz, 1MHz, etc.), fast rise times (e.g., rise times less than about 1 ns, 10ns, 50 ns, 100 ns, 250 ns, 500 ns, 1,000 ns, etc.), fast fall times(e.g., fall times less than about 1 ns, 10 ns, 50 ns, 100 ns, 250 ns,500 ns, 1,000 ns, etc.) and/or short pulse widths (e.g., pulse widthsless than about 1,000 ns, 500 ns, 250 ns, 100 ns, 20 ns, etc.).

Indeed, as used throughout this disclosure, the term “high voltage” mayinclude a voltage greater than 1 kV, 10 kV, 20 kV, 50 kV, 100 kV, etc.;the term “high frequency” may be a frequency greater than 1 kHz, 10 kHz,100 kHz, 200 kHz, 500 kHz, 1 MHz, etc., the term “fast rise time” mayinclude a rise time less than about 1 ns, 10 ns, 50 ns, 100 ns, 250 ns,500 ns, 1,000 ns, etc.; the term “fast fall time” may include a falltime less than about 1 ns, 10 ns, 50 ns, 100 ns, 250 ns, 500 ns, 1,000ns, etc.); and the term short pulse width may include pulse widths lessthan about 1 ns, 10 ns, 50 ns, 100 ns, 250 ns, 500 ns, 1,000 ns, etc.).

Additionally, the term ‘rise time’ may be understood to describe theapplication of voltage and/or charge/and/or energy and/or current to thecircuit at the beginning of the pulse, irrespective of whether the pulseis positive going of negative going with respect to ground. Similarly,the term ‘fall time’ may be understood to describe the application ofvoltage and/or charge/and/or energy and/or current to the circuit at theend of the pulse, irrespective of whether the pulse is positive going ofnegative going with respect to ground.

FIG. 1 is an example circuit 100 that can be used to control the voltageon a load ZL, which may be the circuit/system load. The load ZL may be acapacitor, a capacitor in series with a resistor, a capacitor in serieswith an inductor, a dielectric barrier discharge, a plasma load, asemiconductor wafer processing load, and any arbitrary arrangement ofcapacitors, inductors, resistors, and/or other active and/or passivecomponents, etc. In some embodiments, the load ZL may include any loadthat when voltage is applied, and charge is delivered, thecharge/voltage may remain present for longer than desired (e.g., longerthan the designed or desired fall time). For instance, this may oftenoccur in high voltage switching applications.

In some embodiments, the switch S1 may be a single switch, a seriesstack of switches, a switching power supply, a pulser, a microsecondpulser, an arbitrary pulse generator, or any system that may be used toapply a high voltage, time varying power to the load ZL with theparameters noted above. In some embodiments, the switch S1 can deliverpulses to the load (e.g., charge or power to the load ZL and/orestablish a voltage on the load ZL) at high pulse voltage (e.g.,voltages greater than 1 kV, 10 kV, 20 kV, 50 kV, 100 kV, etc.), highfrequencies (e.g., frequencies greater than 1 kHz, 10 kHz, 100 kHz, 200kHz, 500 kHz, 1 MHz, etc.), fast rise times (e.g., rise times less thanabout 1 ns, 10 ns, 50 ns, 100 ns, 250 ns, 500 ns, 1,000 ns, etc.), fastfall times (e.g., fall times less than about 1 ns, 10 ns, 50 ns, 100 ns,250 ns, 500 ns, 1,000 ns, etc.) and/or short pulse widths (e.g., pulsewidths less than about 1,000 ns, 500 ns, 250 ns, 100 ns, 20 ns, etc.).

In some embodiments, the switch S2 may be a single switch, a seriesstack of switches, or any other arrangement of active elements that canbe used to remove charge from the load ZL and/or reduce the voltageacross the load ZL. In some embodiments, the switch S2 may be used toremove charge from the load ZL when the switch S1 is open. In someembodiments, the switch S2 may be coupled with a resistor.

FIG. 2 is another example circuit 200 according to some embodiments. Inthis example, the switch S1 may be in series with a DC power supply Pand/or may include a transformer or other circuit elements. the switchS1, can include a solid-state switch such as, for example, an IGBT, GaN,MOSFET, etc. switch. the switch S2 may be a switch (e.g., a high voltageswitch), and the load ZL may be represented as a capacitive load CL.

Pulses from the switch S1 and the power supply P may be delivered in thefollowing manner. When the switch S1 is closed and switch S2 is open,charge is delivered to capacitive load CL and the voltage on thecapacitive load CL increases to some value V, set by the power supply P.When the switch S1 is opened, the charge/voltage will remain oncapacitive load CL until the switch S2 is closed and the voltage/chargeis discharged from the capacitive load CL. The pulses from the switch S1and the power supply P may include high pulse voltage (e.g., voltagesgreater than 1 kV, 10 kV, 20 kV, 50 kV, 100 kV, etc.), high frequencies(e.g., frequencies greater than 1 kHz, 10 kHz, 100 kHz, 200 kHz, 500kHz, 1 MHz, etc.), fast rise times (e.g., rise times less than about 1ns, 10 ns, 50 ns, 100 ns, 250 ns, 500 ns, 1,000 ns, etc.), fast falltimes (e.g., fall times less than about 1 ns, 10 ns, 50 ns, 100 ns, 250ns, 500 ns, 1,000 ns, etc.) and/or short pulse widths (e.g., pulsewidths less than about 1,000 ns, 500 ns, 250 ns, 100 ns, 20 ns, etc.).

In some embodiments, there may be an asymmetry between the switch S1 andthe switch S2. For example, many different topologies can be used tocreate a voltage source (the switch S1) that has a high voltage outputcompared to the voltage hold off rating of the actual switches used. Forexample, the switch S1 may include a 600 V switch combined with a 10:1Step up transformer that together produces an output voltage of 6 kV. Inthis example, the switch S2 would need to be a 6 kV rated switch. Whilea 600 V switch may be common, a 6 kV switch is uncommon. In thisexample, the switch S2 must hold off 6 kV until it is closed and removesthe charge/voltage from the load CL. This asymmetry between the switchS1 and the switch S2 may be especially problematic with solid-stateswitches, for example IGBTs, GaN switches, MOSFETs, etc. It can be evenmore problematic when fast switching transition times are required,and/or high frequency operation is required, and/or high voltageoperation is required, since often switches with the required propertieddo not exist.

FIG. 3 is a circuit 300, for example, that can be used to overcome theasymmetry between the switch S1 and the switch S2, and/or the challengesof operating the switch S2 at high frequency, high voltage, and/or withfast rise/fall times. The switch S1 may be a switch in series with a DCpower supply (e.g., as shown in FIG. 2) and/or may include atransformer. The switch S1, for example, can include a solid-stateswitch such as, for example, an IGBT, GaN, MOSFET, etc. switch. Thecircuit element Zp may comprise a resistive output stage that mayinclude a combination of resistors, capacitors, diodes, and/orinductors. In some embodiments, the circuit element Zp may include aseries and/or parallel arrangement of passive elements (i.e. resistors,capacitors, inductors, diodes, etc.). In some embodiments, Zp may bepurely resistive in nature. In some embodiments, the circuit element Zpmay replace the functionality of the switch S2. For example, the circuitelement Zp may allow charge and/or voltage to be removed from the loadZL at high frequency, high voltage, fast rise times, and/or fast falltimes. In terms of voltage, frequency, rise time, and fall time, passiveelements may have fewer constraints compared with solid state switches.

FIG. 4 is an example circuit 400 where circuit element Zp is representedas a resistor R. In this example, the switch S1 closes and establishes avoltage V across capacitive load CL that is set by the power supply P.While the switch S1 is closed, power supply P may maintain the voltage Vacross resistor R and load CL. Once the switch S1 opens, thecharge/voltage on the capacitive load CL can be removed by the resistorR, on a timescale set by the product of (R) and (CL) which is commonlysimply known as an RC timescale. If R was 100 Ohms and C was 1 nF thanthe characteristic voltage fall time given by RC would be 100 ns. Theresistor R can operate in a high voltage, high frequency, fast risetime, and/or fast fall time parameter space within which few to noswitches can operate.

For example, resistor R can remove charge/voltage from capacitive loadCL at 6 kV, 100 kHz, and/or with a 100 ns fall time. Resistor R, forexample, could be selected to remove charge at high pulse voltage (e.g.,voltages greater than 1 kV, 10 kV, 20 kV, 50 kV, 100 kV, etc.), highfrequencies (e.g., frequencies greater than 1 kHz, 10 kHz, 100 kHz, 200kHz, 500 kHz, 1 MHz, etc.), fast rise times (e.g., rise times less thanabout 1 ns, 10 ns, 50 ns, 100 ns, 250 ns, 500 ns, 1,000 ns, etc.), fastfall times (e.g., fall times less than about 1 ns, 10 ns, 50 ns, 100 ns,250 ns, 500 ns, 1,000 ns, etc.) and/or short pulse widths (e.g., pulsewidths less than about 1,000 ns, 500 ns, 250 ns, 100 ns, 20 ns, etc.).This set of voltages, frequencies, rise times, and/or fall times maycover a space not accessible by any existing solid-state switch.

In some embodiments, a resistive output stage can be useful for pulseswith voltages greater than about 1.5 kV, frequencies greater than about10 kHz, pulses widths less than about 100 μs, and/or rise and fall timesshorter than about 1 μs. In some embodiments, a resistive output stagecan be useful, for example, where the load ZL contains capacitances(e.g., including stray, equivalent, effective, etc., or things thatwould be modeled as capacitances) with values smaller than 1 μF. In someembodiments, a resistive output stage can be used with a high voltagepulser for the production of plasmas (which will typically have theplasma and/or electrode/grid scale size less than 1 m or an electrodegrid scale less than about 1 square meter) or involve grids and plateswith scale sizes less than 1 m.

FIG. 5 is another example circuit 500. In circuit 500, circuit elementZp includes resistor R in series with inductor L. In this example,inductor L can be used to reduce the power that flows into resistor Rwhile the switch S1 is closed on short time scales such as, for example,on time scales as can be determined by V=Ldi/dt (e.g., 1 ns, 10 ns, 50ns, 100 ns, 250 ns, 500 ns, 1,000 ns, etc.). Inductor L, for example,can be selected to create a faster fall time and/or faster rise timethan could be achieved for a given value of R.

In some embodiments, circuit element Zp can be used to removevoltage/charge from a load ZL in a parameter space not readilyaccessible to solid-state switches. This parameter space, for example,may include pulses with high pulse voltage (e.g., voltages greater than1 kV, 10 kV, 20 kV, 50 kV, 100 kV, etc.), high frequencies (e.g.,frequencies greater than 1 kHz, 10 kHz, 100 kHz, 200 kHz, 500 kHz, 1MHz, etc.), fast rise times (e.g., rise times less than about 1 ns, 10ns, 50 ns, 100 ns, 250 ns, 500 ns, 1,000 ns, etc.), fast fall times(e.g., fall times less than about 1 ns, 10 ns, 50 ns, 100 ns, 250 ns,500 ns, 1,000 ns, etc.) and/or short pulse widths (e.g., pulse widthsless than about 1,000 ns, 500 ns, 250 ns, 100 ns, 20 ns, etc.). ZL maybe largely capacitive in nature, and/or may contain capacitance, and/ormay represent a capacitance of a wafer and/or plasma. ZL may representany type of capacitive load.

In some embodiments, voltage waveforms can be produced with a singleswitch (or single group of switches) when other topologies might requiretwo-switches (or two groups of switches) to achieve a similar result.For instance, in some embodiments, a single switch (or single group ofswitches) on the input can provide a solution to a problem thatgenerally requires two-switches to solve.

The set of loads ZL where the circuit element Zp may be applicable mayinclude loads that generally have a sufficiently high impedance that theload holds charge/voltage for a longer timescale than desired (e.g.,where desired time scales are on the order of 1 ns, 10 ns, 50 ns, 100ns, 250 ns, 500 ns, 1,000 ns, etc.). In some embodiments, circuitelement Zp may allow for rapid removal of this charge/voltage to achievefast fall times, high frequencies, and/or short pulses.

In some embodiments, a load (e.g., capacitive load CL or generalizedload ZL) may include capacitive loads, electrodes, plasma loads,dielectric barriers, semiconductor fabrication plasmas, semiconductorloads, grids, medical loads, etc. Such loads may, for example, have ahigh impedance compared to the timescale on which charge/voltage needsto be removed from them, such that the load itself does not naturallyproduce the needed voltage/charge removal timescale.

In some embodiments, a load may have stray elements that have a highimpedance compared to the timescale on which charge/voltage needs to beremoved from them. For example, if the load ZL is non-capacitive, butthe load ZL is associated with a parallel stray capacitance, thencircuit element Zp can be used to remove charge/voltage from the straycapacitance, thus allowing the voltage on the load ZL to fall.

In circuits operating at low voltage, it is often common and easy tohave pulse generators that both source and sink current, for example‘data pulsers’. Thus, it does not matter if the load has a highimpedance compared to the timescale on which charge/voltage needs to beremoved from it. The low voltage pulse generator naturally does this byboth sourcing and sinking current, often through the use of twoswitches, where one delivers charge/voltage from a power supply, and theother sinks charge/voltage to ground. At high voltage, high frequencywith short pulse widths and/or fast rise time and/or fall times, suchsourcing and sinking power supplies often do not exist. A resistiveoutput stage may, for example, allow for the sinking of current from theload, and when used in combination with a high voltage pulser thatsources current, allows the equivalent low voltage sourcing and sinkingpower supply to be realized, but at high voltage, high frequency withshort pulse widths and/or fast rise times and/or fast fall times.

The use of a resistive output stage to achieve high voltage pulses athigh frequencies that have fast rise/fall times, and short pulse widthsmay constrain the selection of the circuit elements in the resistiveoutput sage. The resistive output stage may be selected to handle highaverage power, high peak power, fast rise times and/or fast fall times.For example, the average power rating might be greater than about 0.5kW, 1.0 kW, 10 kW, 25 kW, etc., the peak power rating might be greaterthan about 1 kW, 10 kW, 100 kW, 1 MW, etc., and/or the rise and falltimes might be less than 1000 ns, 100 ns, 10 ns, or 1 ns.

The high average power and/or peak power requirement may arise both fromthe need to dissipate stored energy in the load rapidly, and/or the needto do so at high frequency. For example, if the load is capacitive innature, with a 1 nF capacitance that needs discharging in 20 ns, and ifthe resistive output stage may be purely resistive, the resistive outputstage may have a resistance value of about 20 Ohms. If the high voltagepulse applied to the load is 100 ns long at 20 kV, then each pulse willdissipate about 2 J during the 100 ns pulse width (e.g., E=t_(p)V²/R)and an additional 0.2 J draining the stored energy from the 1 nFcapacitive load (e.g., E=½t_(p)CV²), where t_(p) is the pulse width, Vis the pulse voltage, R is the resistance of the resistive output stage,C is the capacitance of the load, and E is the energy. If operated at 10kHz, the total per pulse energy dissipation of 2.2 J may result in anaverage power dissipation of 22 kW into the resistive output stage. Thepeak power dissipation in the resistive output stage during the pulsemay be about 20 MW, and may be calculated from Power=V²/R.

The high frequency and high voltage operation, combined with the needfor the resistance in the resistive output stage to be small, forexample, may lead to examples with either or both high peak power andhigh average power dissipation within the resistive output stage.Standard pulldown resistors that are used in TTL type electricalcircuits and/or data acquisition type circuits (e.g., around 5 volts)usually operate far below 1 W for both average and peak powerdissipation.

In some embodiments, the ratio of the power the resistive output stagedissipates compared to the total power dissipated by the load may be10%, 20% 30% or greater, for example. In standard low voltage electroniccircuits, pull down resistors dissipate less than 1% of the powerconsumed, and typically much less.

The fast rise time and/or fast fall time requirements may constrain boththe allowable stray inductance and/or stray capacitance within theresistive output stage. In the above example, for the 1 nF capacitiveload to be discharged in around 20 ns, the series stray inductance inthe resistive output stage may be less than around 300 nH. For theresistive output stage to not waste significant additional energy due toits stray capacitance, for example, less than 10% of the capacitiveenergy stored in the load capacitance, then the stray capacitance of theresistive output stage may be less than 100 pF. Since the resistiveoutput stage may tend to be physically large due to its high powerdissipation requirements, realizing both this low stray inductance andstray capacitance can be challenging. The design generally requiressignificant parallel and series operation using numerous discretecomponents (e.g., resistors), with the components tightly groupedtogether, and/or spaced far from any grounded surfaces that couldsignificantly increase the stray capacitance.

In some embodiments, a resistive output stage circuit can be used in adielectric barrier discharge device being driven with a high voltagepulser. The load in a dielectric barrier discharge can be dominantlycapacitive. In some embodiments, the load may be modeled as a purelycapacitive load CL, for example, like a dielectric barrier discharge.For example, when the power supply P is switched on, capacitive load CLmay be charged, when power supply P is not switched on, the charge oncapacitive load CL may be drained through resistor R. In addition, dueto high voltages and/or high frequencies and/or fast fall timerequirements a resistive output stage may need to discharge asignificant amount of charge from the capacitive load CL quickly, whichmay not be the case with low voltage applications (e.g., standard 5 Vlogic levels and or low voltage data pulsers).

For example, a typical dielectric barrier discharge device might have acapacitance of about 10 pF and/or may be driven to about 20 kV withabout a 20 ns rise time and/or about a 20 ns fall time. In someembodiments, the desired pulse width might be 80 ns long. For the falltime to match the rise time, a circuit element Zp of about 2 kOhms canbe used to create the desired fall time. Various other values for thecircuit element Zp may be used depending on the load and/or the othercircuit elements and/or the requirements rise time, fall time, and/orpulse width, etc.

In some embodiments, for a capacitive like load, or a load that has aneffective capacitance C (e.g., the capacitance C can be due to the loadZL itself or to additional stray elements), the characteristic pulsefall time can be designated as t_(f) and the pulse rise time can bedesignated by t_(r). In some embodiments, the rise time t_(r) can be setby the specifics of the driving power supply. In some embodiments, thepulse fall time t_(f) can be approximately matched to the pulse risetime t_(r) by selecting the circuit element Zp as a resistor R, wherecircuit element Zp=R=t_(f)/C. In some embodiments, the circuit elementZp can be specifically selected to provide a specific relation betweenthe pulse rise time t_(r) and the pulse fall time t_(f). This isdifferent from the concept of a pull down resistor, where in general, apull down resistor is selected to carry/dissipate voltage/charge on somelonger time scale, and at much lower power levels. Circuit element Zp,in some embodiments, can be specifically used as an alternative to apull down switch, to establish a specific relation between the pulserise time t_(r) and the pulse fall time t_(f).

In some embodiments, if the circuit element Zp is a resistor R, then thepower dissipated in circuit element Zp during a pulse having a pulsewidth t_(p) and a drive voltage V can be found from P=V²/R. Because falltime t_(f) is directly proportional to resistance R (e.g., R=t_(f)/C),as the requirement for fall time t_(f) decreases then the requirementfor the resistance R also decreases, and the power P dissipated incircuit element Zp increases according to P=V²C/t_(f). Thus, circuitelement Zp may be designed to ensure the proper fall time t_(f) yet becapable of handling high power such as, for example, power greater thanabout 1.0 kW, or 100 kW. In some embodiments the resistor may handle theaverage power requirements as well as peak power requirements. The needfor fast fall time t_(f) resulting in low resistance values and theresulting high power dissipation are challenges that can make resistiveoutput stages undesirable as a way to quickly remove charge from acapacitive load CL. In some embodiments, a resistor R can include aresistor with low resistance and yet have a high average power ratingand peak power rating. In some embodiments, the resistor R may include aparallel stack of resistors that collectively have the requiredresistance and power rating. In some embodiments, the resistor R mayinclude a resistor have a resistance less than about 2000 ohms, 500ohms, 250 ohms, 100 ohms, 50 ohms, 25 ohms, 10 ohms, 1 ohm, 0.5 ohms,0.25 ohms, etc., and have an average power rating greater than about 0.5kW, 1.0 kW, 10 kW, 25 kW, etc., and have a peak power rating greaterthan about 1 kW, 10 kW, 100 kW, 1 MW, etc.

Using the example above, with tp=80 ns, V=20 kV, and circuit element Zpset to 2 kOhms, each pulse applied to the load may dissipate 16 mJ oncethe capacitance in the load is fully charged. Once the pulse is turnedoff, charge from the load is dissipated by Zp. If operated at 100 kHz,then circuit element Zp may dissipate 1.6 kW. If circuit element Zp hadbeen selected to create a 10 ns t_(f), then the power dissipated incircuit element Zp would be 3.2 kW. In some embodiments, a high voltagepulse width may extend to 500 ns. At 500 ns with t_(f)=20 ns, circuitelement Zp would dissipate 10 kW.

In some embodiments, the power dissipated in the circuit element Zp canbe considered large if it exceeds 10% or 20% of the power consumed bythe load ZL.

When fast fall times t_(f) are needed, then the power dissipation can belarge such as, for example, about one third the total power consumed. Ifcircuit element Zp, for example, includes a resistor R in series with aninductor L, then inductor L can, for example, reduce the power flow intothe resistor R while the voltage V is present and/or hasten the falltime beyond that set by an RC decay.

For example, the time constant L/R can be set to approximately the pulsewidth t_(p), for example, L/R≈t_(p). This, for example, may reduceenergy dissipation and/or shorten the fall time t_(f), (e.g., decreasest_(f)). In some embodiments, R≈C/t_(f)≈C/t_(r), assuming one wanted tomatch t_(f) to t_(r). In this application, disclosure, and/or claims,the symbol “≈” means within a factor of ten.—

As another example, a load ZL can include a circuit that controls theion energy in a plasma chamber of a semiconductor wafer fabricationdevice. FIG. 6, FIG. 7, FIG. 9, and FIG. 11 and FIG. 13 each representintroducing high voltage pulses into a plasma. Some of these examplecircuits, apply high voltage pulses in a manner that controls the ionenergy within the plasma, and specifically that controls the energy theions have as they exit the plasma and impact, for example, a wafer orother substrate that bounds the plasma.

FIG. 6 is one example of a circuit 600 representing a circuit used toset the ion energy in a plasma chamber of a semiconductor waferfabrication device. The driving waveform may include high voltage andhigh frequency short pulses with a high duty cycle and fast rise timesand fall times. The pulses create a negative bias within the plasma thataccelerates ions to the desired potential, prior to their impact with awafer. An example of such a waveform is shown as waveform 810 in FIG. 8.In waveform 810, a steady negative bias of approximately −4 kV isrealized, through the use of short positive going pulses shown bywaveform 805. The driving waveform to the plasma may include any circuitdescribed in this document where the plasma is the load.

The capacitor C2 represents the capacitance of the dielectric materialupon which a semiconductor wafer sits during fabrication. The capacitorC3 represents the sheath capacitance between a semiconductor surface anda plasma. The current source I1 represents the current of positive ionsmoving from the plasma toward the surface of the wafer. In this example,a portion of the plasma is electrically connected to ground. Thus, anegative electric potential in the plasma between ground and the surfaceof the wafer will induce positive ions to flow and impact the surface ofthe wafer. The capacitor C1 represents the capacitance of leads runninginto the chamber, as well as other stray capacitive elements. In someembodiments, capacitor C1 may have a capacitance of about 40-4,000 pF(e.g., 400 pF), capacitor C2 may have a capacitance of about 0.7-70 nF(e.g., 7 nF), capacitor C3 may have a capacitance of about 10-1,000 pF(e.g., 100 pF), and current source I1 may produce current of about 300mA-30 A (e.g., 3 A). Various other values may be used. Component valueswithin an order of magnitude or so of these element values given mayalso be used.

In some embodiments, the capacitance of the capacitor C1 is almost thesame size as the capacitance of the capacitor C3; and the capacitance ofthe capacitor C2 is large in comparison with the capacitance of thecapacitor C3.

FIG. 7 is a circuit diagram of circuit 700 that includes a pulser 705, aresistive output stage 710, that produces high voltage pluses in aplasma represented by circuit 600. In this example, the resistive outputstage 710 includes inductor L1 and resistor R1. The circuit elements tothe left of inductor L1 and resistor R1 comprise one representation of ahigh voltage pulser 705. In this example, the high voltage pulser 705can produce a plurality of high voltage pulses with a high frequency andfast rise times and fall times. In all of the circuits shown, the highvoltage pulser may comprise a nanosecond pulser.

The various values of the circuit elements in circuit 700 and/or thecircuit 600 may vary. For example, the value of capacitor C3 may beabout 150 pF, the value of capacitor C1 may be about 400 pF, the valueof capacitor C2 may be about 8 nF, the value of inductor L2 may be about300 nH, the value of resistor R1 may be about 150 Ohms, the value ofinductor L1 may be about 6 uH, the value of DC power supply V1 may beabout 5 kV, and/or the value of current source I1 may be about 2 A.Values within an order of magnitude or so of these values may also beused.

FIG. 8 shows example waveforms produced in circuit 700. In this example,the pulse waveform 805 may represent the voltage provided by the pulserstage 705. As shown, the pulse waveform 805 produces a pulse with thefollowing qualities: high voltage (e.g., greater than about 4 kV asshown in the waveform), a fast rise time (e.g., less than about 200 nsas shown in the waveform), a fast fall time (e.g., less than about 200ns as shown in the waveform), and short pulse width (e.g., less thanabout 300 ns as shown in the waveform). The waveform 810 may representthe voltage at the surface of a wafer represented in circuit 700 by thepoint between capacitor C2 and capacitor C3 or the voltage acrosscapacitor C3. The pulse waveform 815 represent the current flowing fromthe pulser 705 to the plasma. The circuit 700 may or may not includeeither or both diodes D1 or D2.

During the transient state (e.g., during an initial number of pulses notshown in the figure), the high voltage pulses from the pulser 705 chargethe capacitor C2. Because the capacitance of capacitor C2 is largecompared to the capacitance of capacitor C3 and/or capacitor C1, andand/or because of the short pulse widths of the pulses, the capacitor C2may take a number of pulses from the high voltage pulser to fullycharge. Once the capacitor C2 is charged the circuit reaches a steadystate, as shown by the waveforms in FIG. 8.

In steady state and when the switch S1 is open, the capacitor C2 ischarged and slowly dissipates through the resistive output stage 710, asshown by the slightly rising slope of waveform 810. Once the capacitorC2 is charged and while the switch S1 is open, the voltage at thesurface of the waver (the point between capacitor C2 and capacitor C3)is negative. This negative voltage may be the negative value of thevoltage of the pulses provided by the pulser 705. For the examplewaveform shown in FIG. 8, the voltage of each pulse is about 4 kV; andthe steady state voltage at the wafer is about −4 kV. This results in anegative potential across the plasma (e.g., across capacitor C3) thataccelerates positive ions from the plasma to the surface of the wafer.While the switch S1 is open, the charge on capacitor C2 slowlydissipates through the resistive output stage.

When the switch S1 is closed, the voltage across the capacitor C2 mayflip (the pulse from the pulser is high as shown in waveform 805) as thecapacitor C2 is charged. In addition, the voltage at the point betweencapacitor C2 and capacitor C3 (e.g., at the surface of the wafer)changes to about zero as the capacitor C2 charges, as shown in waveform810. Thus, the pulses from the high voltage pulser produce a plasmapotential (e.g., a potential in a plasma) that rise from a negative highvoltage to zero and returns to the negative high voltage at highfrequencies, with fast rise times, fast fall times, and/or short pulsewidths.

In some embodiments, the action of the resistive output stage, elementsrepresented by block 710, that may rapidly discharge the straycapacitance C1, and may allow the voltage at the point between capacitorC2 and capacitor C3 to rapidly return to its steady negative value ofabout −4 kV as shown by waveform 810. The resistive output stage mayallow the voltage at the point between capacitor C2 and capacitor C3 toexists for about 90% of the time, and thus maximizes the time which ionsare accelerated into the wafer. In some embodiments, the componentscontained within the resistive output stage may be specifically selectedto optimize the time during which the ions are accelerated into thewafer, and to hold the voltage during this time approximately constant.Thus, for example, a short pulse with fast rise time and a fast falltime may be useful, so there can be a long period of fairly uniformnegative potential.

FIG. 9 shows another example circuit 900 according to some embodiments.The circuit 900 can be generalized into three stages (these stages couldbe broken down into other stages or generalized into fewer stages). Thecircuit 900 includes pulser stage 905, a lead stage 910, and a loadstage 915. The pulser stage 905 may include pulser and transformer stage906 and a resistive output stage 907.

In some embodiments, the load stage 915 may include a capacitive loadC12. The capacitance of the capacitive load C12 may be on the order ofabout 10 pF. Some examples of a capacitive load may include a dielectricbarrier discharge, a semiconductor fabrication device, a capacitivedevice, a photoconductive switch, a dielectric barrier discharge device,etc. In some embodiments, C12 may be a high voltage grid for ion beams,neutral beams, or any other accelerator or grid for producing rapidlychanging electric fields. In some embodiments, the capacitor C12 may bea stripline kicker.

The pulser stage 905 may include a pulser and transformer stage 906. Thepulser and transformer stage 906 may produce pulses with high pulsevoltage (e.g., voltages greater than 1 kV, 10 kV, 20 kV, 50 kV, 100 kV,etc.), high frequencies (e.g., frequencies greater than 1 kHz, 10 kHz,100 kHz, 200 kHz, 500 kHz, 1 MHz, etc.), fast rise times (e.g., risetimes less than about 1 ns, 10 ns, 50 ns, 100 ns, 250 ns, 500 ns, 1,000ns, etc.), fast fall times (e.g., fall times less than about 1 ns, 10ns, 50 ns, 100 ns, 250 ns, 500 ns, 1,000 ns, etc.) and/or short pulsewidths (e.g., pulse widths less than about 1,000 ns, 500 ns, 250 ns, 100ns, 20 ns, etc.).

In this example, the resistive output stage 907 includes threeresistors: resistor R1, resistor R2, and resistor R4. In someembodiments, resistor R1 and resistor R2 may have the same resistancevalues. In some embodiments, resistor R1 and resistor R2 can be selectedfor a number of purposes. For example, resistor R1 and resistor R2 canhave resistance levels selected to limit the current flowing from thepulser stage 905 to the load stage 915. As another example, resistor R1and resistor R2 can have resistance levels selected to determine therise time t_(r) and the fall time t_(f), which may also depend on theinductance in the lead stage 910 (e.g., inductor L2 and inductor L6)and/or the capacitance of the load stage (e.g., capacitance C12). Insome embodiments, the resistance values of resistor R1 and resistor R2can be set based on a specific application. In some embodiments,resistor R1 and resistor R2 can be used to protect against load shortssuch that all the current from the pulse and transformer circuit 906 canbe dissipated in resistor R1 and resistor R2. In some embodiments,resistor R2 and/or inductor L6 may be set to approximately zero, suchthat their side of C12 can be ground referenced.

A pulse from the pulser and transformer stage 905 may charge thecapacitive load C12 in the load stage 915. While the pulse is chargingthe capacitive load C12, most of the current may charge the capacitiveload C12, and some current may flow through resistor R4. Once thecapacitive load C12 is fully charged, most if not all the current flowsthrough resistor R4. Because of the high voltages applied by the pulserand transformer stage 905 and noting that the power dissipated throughresistor R4 is inversely proportional to the resistance of resistor R4,resistor R4 may have a high power rating (e.g., both average power andpeak power). In some embodiments, the resistance value of R4 can beselected in conjunction with the value of the load capacitance C12 sothat the fall time t_(f) can be fast e.g., less than 1 ns, 10 ns, 50 ns,100 ns, 250 ns, 500 ns, 1,000 ns, etc.

FIG. 10 is another example circuit 1000 according to some embodiments.The circuit 1000 can be generalized into five stages (these stages couldbe broken down into other stages or generalized into fewer stages). Thecircuit 1000 includes pulser and transformer stage 906, a resistiveoutput stage 1007, a lead stage 910, load crowbar stage 1010, and a loadstage 1015.

The pulser and transformer stage 906 are as described in FIG. 9.

In this example, the resistive output stage 1007 may include a blockingdiode D1 that can ensure that current from the load stage 1015 (or fromanywhere else) does not flow back into the pulser and transformer stage906. The capacitor C4 may represent the stray capacitance of theblocking diode D1.

In some embodiments, the resistive output stage 1007 may include one ormore inductive elements represented by inductor L1, inductor L2,inductor L8, and/or inductor L10. These inductive elements may, forexample, limit current flow from the capacitive load in the load stage1015. In some embodiments, the resistor R2 may dissipate charge from thecapacitive load C1 in the load stage 1015, for example, on fast timescales (e.g., 1 ns, 10 ns, 50 ns, 100 ns, 250 ns, 500 ns, 1,000 ns, etc.time scales). The resistance of resistor R2 may be low to ensure thepulse across the load stage 1015 has a fast fall time t, for example afall time less than 1 ns, 10 ns, 100 ns, or 1000 ns. The inductiveelements, for example, inductor L2 may limit the current flow throughresistor R2, and may increase the overall circuit efficiency.

In this example, the load crowbar stage 1010, includes a diode D5 whichmay ensure that the current to the load stage 1015 does not reversepolarity. In some embodiments, the stray inductance of the crowbar stage1010 is represented by L7 and the stray capacitance of the diode D5 isrepresented by C9. In some embodiments, stray resistance of the crowbarstage 1010 may be represented by resistor R4. Resistance R4 may beintentionally added to create voltage waveforms of a particular desiredshape across load 1015.

In this example, the load stage 1015 may include either or bothresistive and capacitance elements represented by resistor R1 andcapacitor C1. The capacitance of capacitor C1 may, for example, be onthe order of about 10 nF. Some examples of a capacitive and resistiveload may include a charging a capacitor for energy storage purposes in aphotoconductive switch which may be used to produce high powermicrowaves. In such circuits, it is important that the load capacitanceonly be charged for short periods of time, and the resistive outputstage provides a path to rapidly remove (sink) charge from the loadshould it not otherwise be removed by the action of other circuitelements that are not shown in this figure. The resistive output stagemay also ensure that the voltage across C1 is constant at the start ofevery charge cycle, assuming the charge repetition rate is slow comparedto the discharge rate of C1 through the resistive output stage. In thisexample, the resistive output stage rapidly returns the potential acrossC1 to zero.

FIG. 11 shows another example circuit 1100 according to someembodiments. The circuit 1100 can be generalized into five stages (thesestages could be broken down into other stages or generalized into fewerstages). The circuit 1100 includes pulser and transformer stage 906, aresistive output stage 1107, a lead stage 910, a DC bias power supplystage 1110, and a load stage 1115.

In this example, the load stage 1115 may represent an effective circuitfor a plasma deposition system, plasma etch system, or plasma sputteringsystem. The capacitance C2 may represent the capacitance of thedielectric material upon which a wafer may sit. The capacitor C3 mayrepresent the sheath capacitance of the plasma to the wafer. Thecapacitor C9 may represent capacitance within the plasma between achamber wall and the top surface of the wafer. The current source I2 andthe current source I1 may represent the ion current through the sheath.

In this example, the resistive output stage 1107 may include one or moreinductive elements represented by inductor L1 and/or inductor L5. Theinductor L5, for example, may represent the stray inductance of theleads in the resistive output stage 1107. Inductor L1 may be set tominimize the power that flows directly from the high voltage supply 906into resistor R1.

In some embodiments, the resistor R1 may dissipate charge from the loadstage 1115, for example, on fast time scales (e.g., 1 ns, 10 ns, 50 ns,100 ns, 250 ns, 500 ns, 1,000 ns, etc. time scales). The resistance ofresistor R1 may be low to ensure the pulse across the load stage 1115has a fast fall time t_(f).

In some embodiments, the resistor R1 may include a plurality ofresistors arranged in series and/or parallel. The capacitor C11 mayrepresent the stray capacitance of the resistor R1 including thecapacitance of the arrangement series and/or parallel resistors. Thecapacitance of stray capacitance C11, for example, may be less than 500pF, 250 pF, 100 pF, 50 pF, 10 pF, 1 pF, etc. The capacitance of straycapacitance C11, for example, may be less than the load capacitance suchas, for example, less than the capacitance of C2, C3, and/or C9.

In some embodiments, a plurality of pulser and transformer stages 906can be ganged up in parallel and coupled with the resistive output stage1107 across the inductor L1 and/or the resistor R1. Each of theplurality of pulser and transformer stages 906 may each also includediode D1 and/or diode D6.

In some embodiments, the capacitor C8 may represent the straycapacitance of the blocking diode D1. In some embodiments, the capacitorC4 may represent the stray capacitance of the diode D6.

In some embodiments, the DC bias power supply stage 1110 may include DCa voltage source V1 that can be used to bias the output voltage eitherpositively or negatively. In some embodiments, the capacitor C12isolates/separates the DC bias voltage from the resistive output stageand other circuit elements. It allows for a potential shift from oneportion of the circuit to another. In some applications the potentialshift it establishes is used to hold a wafer in place. Resistance R2 mayprotect/isolate the DC bias supply from the high voltage pulsed outputfrom circuit component group 906

FIG. 12 shows another example circuit 1200 according to someembodiments. Circuit 1200 is similar to circuit 900 shown in FIG. 9.Resistive output stage 1207, in this example, however, includes switchS2, which may open and close based on a signal from voltage supply V1.The switch S2, for example, may be open while the load stage 915 isbeing charged by a signal from the pulser and transformer stage 906 suchas, for example, when the switch(s) S1 in pulser and transformer stage906 is closed. The switch S2, for example, may be closed to dischargeany charge in the load stage 915 such as, for example, when theswitch(s) S1 in pulser and transformer stage 906 is open. Because of thehigh voltages applied to the load stage 915, the voltages applied acrossthe switch S2 will be large requiring a switch that is rated for highvoltages. In addition, to allow for fast rise times and fast fall timesat the load stage 915, the switch S2 may be required to switch quickly.Resistor R1 and resistor R2 may be small, and may represent strayresistance contained within conductors and cables. Resistor R4 may beselected to set a particular fall time for the energy/voltagedissipation from the load.

In another example, resistor R2 and inductor L6 may be about zero. Thismay allow the low side to be ground referenced, and may effectivelycreate a single sided circuit topology instead of the differentialoutput topology shown.

FIG. 13 shows another example circuit 1300. Circuit 1300 is similar tocircuit 1100 shown in FIG. 11. Resistive output stage 1307, in thisexample, however, includes switch S2, which may open and close based ona signal from voltage supply V1. The switch S2, for example, may be openwhile the load stage 1115 is being charged by a signal from the pulserand transformer stage 906 such as, for example, when the switch(s) S1 inpulser and transformer stage 906 is closed. The switch S2, for example,may be closed to discharge any charge in the load stage 1115 such as,for example, when the switch(s) S1 in pulser and transformer stage 906is open. Because of the high voltages applied to the load stage 1015,the voltages applied across the switch S2 will be large requiring aswitch that is rated for high voltages. In addition, to allow for fastrise times and fast fall times at the load stage 1015, the switch S2 maybe required to switch quickly. The resistor R1 may be selected torealize particular circuit rise times and/or fall times.

In some embodiments, the switch S2 described in FIG. 12 and/or FIG. 13may include a high voltage switch. A high voltage switch may include aplurality of solid-state switches arranged in series.

Some embodiments include a high voltage switching power supply (e.g.,switch S1 in FIG. 1 and FIG. 3, switch S1 and power supply P1 in FIG. 2,FIG. 4, and FIG. 5, FIG. 7, FIG., switch S2 and power supply V2 in FIGS.9-13). Any type of high voltage switching power supply may be used thatcan produce high voltages at high frequencies with fast rise times andfast fall times. One example of a high voltage switching power supplyincludes nanosecond pulsers described in U.S. patent application Ser.Nos. 14/542,487, 14/635,991, and 14/798,154, which are incorporated intothis document in their entirety for all purposes. Other examples of highvoltage switching power supplies are described below.

Systems and methods are disclosed to provide high voltage and/or highpower output waveforms with programmable control from Direct Current(DC) to greater than 100 kHz pulses with controllable duty cycles from 0to 100%. In some embodiments, a system can include a pulse generatorthat is galvanically isolated.

There are number of potential challenges that must be overcome whendesigning a high voltage pulse generator. For example, slow rise timescan be detrimental to a high voltage pulse generator especially whenswitching at high frequencies. For example, a high frequency pulsegenerator may not be able to switch quickly enough if the rise time islonger than the pulse period because the pulse may not reach the peakvoltage before being switched off again.

As another example, a high voltage pulse generator may also smooth ahigh frequency input signal to generate a high voltage output signalthat has a voltage higher than the input signal. In order to accomplishsuch smoothing, may require that the input signal include at least oneof a high frequency, fast rise times, and fast fall times. In someembodiments, the high frequency of the input signal may be five to tentimes greater than the output signal. Moreover, the higher the inputfrequency of the input signal, the smoother the output signal.

In some embodiments, the pulse generator may generate high voltagepulses with fast rise times of various types such as, for example,square waves, sinusoidal waves, triangular waves, arbitrary waves, longsingle pulses, multiple pulses, etc.

In some embodiments, a pulse generator may generate high voltage pulseshaving an arbitrary waveform that has a fast rise time (e.g., less than1 μs). In some embodiments, a pulse generator may generate a highvoltage pulses that have a variable duty cycle or user controlled dutycycle.

In some embodiments, a pulse generator can output high voltage greaterthan 0.5 kV, 1.0 kV, 2.0 kV, 5.0 kV, 10 kV, 15 kV, 20 kV, 25 kV, 50 kV,100 kV, or 1,000 kV.

In some embodiments, the input signal may be greater than about 50 kHzor 100 kHz.

Embodiments described within this document do not include, for example,DC-DC converters, despite that some embodiments may be capable ofgenerating a DC output. For example, a pulse generator does not simplyconvert a source of direct current (DC) from one voltage level toanother. Indeed, embodiments described within this document aredifferent than other pulse generators and/or different than DC-DCconverters. For example, embodiments described within this document arenot optimized for converting direct current from one voltage to anotherlevel. As another example, a pulse generator may produce pulses withlong pulse widths, fast rise times, and/or fast fall times, but does notin general produce a DC output signal. Instead, some embodimentsdescribed within this document may produce high voltage pulses with fastrise times and/or fast fall times. Some embodiments described withinthis document may produce high voltage pulses having a long high voltagepulse or with a long pulse width that have a fast rise time and/or afast fall time. Some embodiments described within this document mayproduce high frequency and high voltage pulses with any waveform shape.As another example, embodiments described within this document mayproduce one or more waveforms and/or signals with specificallydesignated very low frequency components as well as waveforms withspecifically designated very high frequency components. Moreover, insome embodiments, a pulse generator may produce waveforms that aregalvanically isolated from a reference potential (e.g., ground).

FIG. 14 is an example block diagram of a pulse generator 100 accordingto some embodiments. The pulse generator 100 may include one or morestages or blocks as shown in the figure. One or more of these stages maybe removed, replaced with another stage, and/or combined with anotherstage. A driver stage 105 that includes any components or devices thatmay push or pull current. The driver stage 105 is coupled with a balancestage 110. The balance stage 110 can be used, for example, to keep atransformer stage 115 from saturating due to imbalanced current. Thedriver stage may include one or more energy sources, switches, bridges,etc. The one or more switches may include, for example, one or moreIGBTs, switches, solid state switches, MOSFET, may be used to switch theenergy source. As another example, the driver stage may include awaveform generator that may be used to produce an input waveform. Insome embodiments, a waveform that is to be amplified may be provided tothe driver from an external source. In some embodiments, an IGBTcircuit(s) may be used with the driver stage 105 such as, for example,the IGBT circuit discussed in U.S. patent application Ser. No.13/345,906, entitled Efficient IGBT Switching the entirety of which isincorporated by reference in its entirety.

In some embodiments, the driver stage 105 may include an H-bridge, ahalf bridge, or a full bridge. An example of a full bridge configurationis shown in FIG. 17. Any number of configurations of input sources maybe used without limitation. Various other configurations or circuits maybe included such as, for example, resonant topologies and push-pulltopologies.

At fixed voltage, the time rate of change of current through a givencircuit may be inversely proportional to the inductance of the circuit.Thus, in some embodiments, in order to produce fast rise times, thedriver stage 105, for example, may have a low total inductance. In someembodiments, the driver stage 105 may have a total inductance below1,000 nH. In some embodiments, the inductance of all components,circuits, elements, etc. prior to a transformer or transformers of atransformer stage may have a total inductance less than 1,000 nH. Insome embodiments, the inductance of all components, circuits, elements,etc. including the primary winding of one of more transformers of thetransformer stage 115 may have an inductance less than 1,000 nH. In someembodiments, the inductance of all components, circuits, elements, etc.om the driver stage 105 and the balance stage 110 may have a totalinductance less than 1,000 nH.

In some specific embodiments, the driver stage 105 may have a totalinductance below 1,000 nH. In some specific embodiments, the inductanceof all components, circuits, elements, etc. prior to a transformer ortransformers of a transformer stage may have a total inductance lessthan 1,000 nH. In some specific embodiments, the inductance of allcomponents, circuits, elements, etc. including the primary winding ofone of more transformers of the transformer stage 115 may have aninductance less than 1,000 nH. In some specific embodiments, theinductance of all components, circuits, elements, etc. om the driverstage 105 and the balance stage 110 may have a total inductance lessthan 1,000 nH.

The balance stage 110 may also be coupled with the transformer stage 115that may include one or more transformers each having any number ofcoils. The transformer stage 115 may also increase the voltage from thedriver stage 105 and/or the balance stage 110 depending on the number ofwinds on either side of the transformer stage 115. The transformer stage115 may provide, for example, galvanic isolation between the driverstage 105 and the output stage 135. The transformer stage 115 may alsoprovide, for example, step up from the input voltage provided by thedriver stage 105 to an increased voltage output.

The transformer stage 115 may be coupled with a rectifier stage 120. Thefilter stage 125 may be coupled with the rectifier stage 120. The filterstage 125 may include any number of components such as, for example,active components (e.g., switches, diodes, etc.) and/or passivecomponents (e.g., inductors, capacitors, resistors, etc.)

The transformer stage may include a transformer that transforms an inputsignal into a high voltage output signal. The high voltage output signalmay have a voltage of 500 volts, 1,000 volts, 2000 volts, 10,000 voltsand/or 100,000 volts, or higher.

The sink stage 130 may be placed after the filter stage 125 as shown inFIG. 14 or placed before the filter stage 125. The sink stage 130 may,for example, dump energy, sink current, and/or rapidly reverse currentflow of any energy stored in the filter stage 125 and/or the outputstage 135.

The output stage 135 may be coupled with the sink stage 130 as shown inFIG. 14 or may be coupled with the filter stage 125 and/or the rectifierstage 120. The output stage 135 may include the load and/or the deviceto which the output signal is sent. The output stage 135 may begalvanically isolated form a reference signal, from ground, and/or fromthe driver stage 105. In some embodiments, the output stage can befloating or biased to any potential desired (e.g., with the DC biasstage 140). In some embodiments, the output stage 135 may output asignal with a rise time of less than 100 ns and/or a fall time of lessthan 100 ns.

The DC bias stage 140 may be coupled with the output stage 135 and mayinclude any voltage source and/or power source. The DC bias stage 140,for example, may be connected with a reference signal, ground, and/orthe driver stage. In some embodiments, the DC bias stage 140 mayreference the potential of the output stage 135 to the potential of thedriver stage 105 of the pulse generator 100. The DC bias stage 140, forexample, may be coupled to the rectifier stage 120, the filter stage125, the sink stage 130, and/or the output stage 135. The DC bias stage140, for example, may be of any polarity and/or may include any voltage.In some embodiments, the DC bias stage 140 may provide a DC bias signal,for example, having a voltage greater than 0.01 kV, 0.1 kV, 1 kV, 3 kV,10 kV, 30 kV, or 100 kV. In some specific embodiments, the DC biasvoltage may be greater than 0.1 kV or 1 kV.

FIG. 15A is an example driver stage 105 according to some embodimentsdescribed in this document. The driver stage 105, for example, mayinclude any device or components that may push or pull current in thepulse generator 100. The driver stage 105, for example, may include oneor more high voltage power supplies or voltage sources that may providean input voltage of 50 volts, 100 volts, 200 volts, 300 volts, 400volts, 500 volts, 600 volts, 700 volts, 800 volts, 900 volts, etc. toover 4500 volts. The driver stage 105, for example, may include one ormore solid state switches such as, for example, one or more IGBTs and/orone or more MOSFETs that can be used to the switch the high voltagepower supply. In some embodiments, the solid state switches may operateat voltages up to 2 kV or up to 4.5 kV.

In some embodiments, the driver stage 105 may include one or moreH-bridge circuits and/or half-bridge circuits operated in parallel. EachH-bridge circuit may include, for example, one or more solid stateswitches. Moreover, the driver stage 105, for example, may or may not becoupled with a reference signal and/or with ground potential. The one ormore solid state switches, for example, may switch at a frequency of 0.1kHz, 1 kHz, 10 kHz, 100 kHz, 1,000 kHz, 10,000 kHz, etc.

In FIG. 15A, the stray inductance, L1 and L2, of the driver stage 105singularly or in combination may be less than 1 nH, 10 nH, 100 nH, 1,000nH, 10,000 nH, etc. In some specific embodiments, the stray inductanceL1 and/or L2 may be less than 100 nH or 1,000 nH. In some specificembodiments, the stray inductance, L1 and L2, may represent and/orinclude all inductance such as, for example, stray inductance in thecircuit, inductors, inductance in components, etc.

In some embodiments, the driver stage 105 may include one or more powersources that may provide voltage at 50 volts, 100 volts, 200 volts, 300volts, 400 volts, 500 volts, 600 volts, 700 volts, 800 volts, 900 volts,etc. to over 4500 volts. In some specific embodiments, the voltageprovided by the one or more power sources in the driver stage 105 may begreater than 100 V or 500 V.

FIG. 15B is an example balance stage 110 according to some embodimentsdescribed in this document. In FIG. 15B, the balance stage 110 is notused and/or may not include, for example, any active or passivecomponents except, possibly, a connection between the driver stage 105and the transformer stage.

FIG. 15C is another example balance stage 110 according to someembodiments described in this document. In this example, the balancestage 110 includes blocking capacitor C1, which may keep the transformerstage 115 from saturating due to imbalanced current from the driverstage 105. The blocking capacitor C1 may have a capacitance value ofgreater than 1 μF, 10 μF, 100 μF, 1,000 μF, 10,000 μF, etc.

FIG. 15D is another example balance stage 110 according to someembodiments described in this document. In this example, the balancestage 110 includes blocking capacitor C2 and blocking capacitor C3,which may keep the transformer stage 115 from saturating due toimbalanced current from the driver stage 105. The blocking capacitor C2,for example, may have a capacitance value of greater than 1 μF, 10 μF,100 μF, 1,000 μF, 10,000 μF, etc. The blocking capacitor C3 may have acapacitance value of greater than 1 μF, 10 μF, 100 μF, 1,000 μF, 10,000μF, etc.

FIG. 15E is an example transformer stage 115 according to someembodiments described in this document. The transformer stage 115, forexample, may include one or more transformers. A transformer of thetransformer stage 115, for example, may step up the voltage provided bythe driver stage 105 to a higher voltage such as for example, over 500volts, 1500 volts, 2500 volts, 50,000 volts, 250,000 volts, etc.

The transformer, for example, may include a primary side 116 and asecondary side 117. The primary side 116 may have a total effectiveseries stray inductance L3 and L4 that may have an inductance singularlyor in combination of less than 10 nH, 100 nH, 1,000 nH, or 10,000 nH. Insome specific embodiments, the total effective series stray inductanceL3 and L4 may be less than 1,000 nH. In some specific embodiments, thesecondary side 117 may have a total effective parallel stray capacitanceC4 of less than 1 pF, 10 pF, 100 pF, 1,000 pF, 10,000 pF, etc. In somespecific embodiments, the total effective parallel stray capacitance C4may be less than 100 pF or 1,000 pF.

The transformer stage 115 may comprise any type of transformer. In someembodiments, the transformer may include primary windings on the primaryside 116 and secondary windings on the secondary side 117 that are bothwrapped around a magnetic core such as, for example, a ferrite core. Theratio (N_(s)/N_(p)) of the number secondary windings (N_(s)) to thenumber of primary windings (N_(p)) may be greater than 2, 4, 5, 5.5, 8,10, 150, 600, etc.

In some embodiments, the transformer stage 115 may include one or moretransformers arranged in parallel with each other.

In some embodiments, the transformer stage 115 may output a voltagegreater than 1 kV, 2 kV, 5 kV, 10 kV, 30 kV, 100 kV, 300 kV, or 1,000kV.

FIG. 15F is an example rectifier stage 120 according to some embodimentsdescribed in this document. The rectifier stage 120 may include, forexample, total effective series stray inductance L5 and L6 singularly orin combination of less than 10 nH, 100 nH, 1,000 nH, 10,000 nH, etc. Insome specific embodiments, the effective series stray inductance L5 andL6 singularly or in combination may be less than 1,000 nH. In some otherspecific embodiments, the effective series stray inductance L5 and L6singularly or in combination may be less than 100 nH. In someembodiments, the rectifier stage 120 may include total effectiveparallel stray capacitance C5 of less than 1 pF, 10 pF, 100 pF, 1,000pF, 10,000 pF, etc. In some specific embodiments, the capacitance of thetotal effective parallel stray capacitance C5 may be less than 1,000 pF.In some specific embodiments, the capacitance of the total effectiveparallel stray capacitance C5 may be less than 200 pF. The rectifierstage 120 may also include a plurality of diodes, that may be used inseries and/or parallel configurations that are designed and havespecifications sufficient for high voltage and/or high powerapplications.

The rectifier stage 120 may include any type of rectifier such as, forexample, a single phase rectifier, a single phase half wave rectifier, asingle phase full wave rectifier, a full wave rectifier, a three-phaserectifier, a three-phase half wave circuit, a three-phase bridgerectifier, a two pulse bridge, a twelve pulse bridge, etc. In someembodiments, more than one rectifier may be used in series and/orparallel.

The filter stage 125 may include a number of different configurationsdepending on the type of specification and/or application. Threeexamples are shown in FIG. 16A, FIG. 16B, and FIG. 16C. In someembodiments, the filter may include only passive elements such as, forexample, inductors, capacitors, resistors, etc. Various otherconfigurations may be used.

FIG. 16A is an example filter stage 125 according to some embodimentsdescribed in this document. In this configuration, the filter stage 125does not include any components. In this configuration, the output ofthe rectifier stage 120 may be tied directly with the output stage 135and/or the load. This filter stage may be used to produce an outputsignal that includes at least one of fast rise times, fast fall times,and high frequencies, etc.

FIG. 16B is an example filter stage 125 according to some embodimentsdescribed in this document. In this configuration, the filter stage 125may include total effective series inductance L7 and L8 singularly or incombination of less than 0.1 μH, 1 μH, 10 μH, 100 μH, 1,000 μH, 10,000μH, etc. In some specific embodiments, the total effective seriesinductance L7 and L8 singularly or in combination may be less than 30μH. The filter stage 125 may include total effective parallelcapacitance C6 of less than 0.01 nF, 0.1 nF, 1 nF, 10 nF, 100 nF, 1,000nF, etc. In some specific embodiments, the total effective parallelcapacitance C6 may be less than 300 μF or 30 μF. This configuration, forexample, may be used to smooth an input waveform provided by the driverstage 105 and/or allow for an arbitrary waveform.

FIG. 16C is an example filter stage 125 according to some embodimentsdescribed in this document. In this configuration, the filter stage 125may include total effective series inductance L9 and L10 singularly orin combination of less than 0.1 μH, 1 μH, 10 μH, 100 μH, 1,000 μH,10,000 μH, etc. In specific embodiments, the total effective seriesinductance L9 and L10 singularly or in combination may be less than 30μH.

In some embodiments, the filter stage 125 may include total effectiveparallel capacitance C7 of less than 0.01 nF, 0.1 nF, 1 nF, 10 nF, 100nF, 1,000 nF, etc. In some specific embodiments, the total effectiveparallel capacitance C7 may be less than 300 μH or 30 μH. The filterstage 125 may include, for example, total effective parallel resistanceR1 and R2 singularly or in combination of less than 0.1 Ohms, 1 Ohms, 10Ohms, or 100 Ohms. In some specific embodiments, the total effectiveparallel resistance R1 and R2 singularly or in combination may be lessthan 10 Ohms or less than 1 Ohm. This configuration, for example, may beused to smooth an input waveform provided by the driver stage 105 and/orallow for an arbitrary waveform.

Various other configurations of filter stage 125 may be used.

FIG. 16D is an example sink stage 130 according to some embodimentsdescribed in this document. Sink stage 130 may include a switch S1 and aresistance R3. The resistance R3 may include stray resistance and/or aresistor that may be used to limit the current flowing through switchS1. When the switch S1 is closed, the sink stage 130 may rapidly dumpenergy that may be stored in the filter stage 125 and/or the outputstage 135 such as, for example, any energy stored in a capacitor in thefilter stage 125 and/or the output stage 135. In some embodiments, thesink stage 130 may be located between the filter stage 125 and therectifier stage 120. In other embodiments the sink stage 130 may bedisposed between the filter stage 125 and the output stage 135.

FIG. 17 is an example circuit diagram 400 that may comprise all or partof a pulse generator according to some embodiments described in thisdocument. The circuit diagram 400 includes driver stage 105, transformerstage 115, rectifier stage 120, filter stage 125, sink stage 130, andoutput stage 135.

In some embodiments, the output stage 135 can be galvanically isolatedfrom ground, from the driver stage, and/or from any reference potential.

In this embodiment, the filter stage 125 includes a switch S5. Theoutput of the rectifier stage 120 can then be directly switched by theswitch S5.

The sink stage 130 may include switch S6. In some embodiments, switch S5and switch S6 may be fast switches that open and close within 1 μs orfaster. In some embodiments, the switch S5 and/or the switch S6 areswitches that may operate at high frequencies.

When the switch S5 is closed DC power can be sourced to the output stage135 (or the load R22 and/or R11). A graph of the voltage over time atthe output stage 135 is shown in FIG. 18A. If switch S5 is switched onand off, then a pulsed waveform can be sourced to the output stage 135as shown in FIG. 18B and FIG. 18C. Switch S6 can be opened when switchS5 closes and closed when switch S5 opens. When switch S6 is closed,capacitance can be drained from the load capacitance represented as C8.The switches used by switch S5 and/or switch S6 may operate at highpower, high frequency, with variable duty cycle, at variable pulsewidths, etc.

Switch S5 and/or switch S6 may include one or more solid state switchessuch as, for example, one or more MOSFETs and/or one or more IGBTs.Moreover, in some embodiments, switch S5 and/or switch S6 may alsoinclude one or more switches stacked, arranged in parallel, and/orarranged in series.

In some embodiments, a controller may be included that controls theoperation and/or timing of switch S5 and/or switch S6 as the duty cycle,pulse width, and/or frequency are changed and to ensure that switch S5is closed when switch S6 is open and vice-versa. These switches mayinclude solid state switches and/or IGBT circuits discussed in U.S.patent application Ser. No. 13/345,906, entitled Efficient IGBTSwitching the entirety of which is incorporated into this document byreference in its entirety.

In some embodiments, the emitter of switch S5 and/or switch S6 may notbe referenced back to ground. That is, the emitter of switch S5 and/orswitch S6 may be galvanically isolated from all or part of the circuit.Moreover, the gate of switch S5 and/or switch S6 may be isolated using afiber optic receiver and/or a fiber optic device.

In some embodiments, the size, shape, frequency, and/or duty cycle ofpulses produced by the pulse generator may be controllable (or varied byuser input). For example, the pulses can vary from a DC output to a 10MHz output with duty cycles from 0% to 100%. In some embodiments, thegalvanic isolation allows the output waveform potential to be set toarbitrary potential levels with respect to other system potentials. Insome embodiments galvanic isolation may be 500 V, 1 kV, 2 kV, 3 kV, 5kV, 10 kV, 20 kV, 100 kV, etc. with respect to other potentials. Someembodiments include a combination of two or more output stages to bothprovide and to sink high power and/or currents to and from the load. Thecombination of output stages may allow for precise control of arbitrarypulses to be delivered to both resistive and capacitive loads.

FIGS. 18A, 18B and 18C illustrate the variability of the output from apulse generator. FIG. 18A is an example graph of a DC output pulse ofover 2 kV. FIG. 18B is an example graph of an output pulse of over 2 kVpulsing at 100 kHz. And FIG. 18C is an example graph of an output pulseof over 2 kV pulsing at 5 kHz. Various other frequencies and/oramplitudes may be output using embodiments described in this document.

FIG. 19 is an example pulse generator according to some embodimentsdescribed in this document. The pulse generator includes an output stage135, a rectifier stage 120, a transformer stage 115, and a driver stage105.

FIG. 20A is an example circuit diagram 700 of a portion of a pulsegenerator according to some embodiments described in this document. Thecircuit diagram 700 shows a transformer stage 115 that includes a 1:5.5transformer. The circuit diagram 700 also shows a rectifier stage 120, afilter stage 125, and an output stage 135. The filter stage 125 in thisexample includes circuit elements that include two 125 μH inductors andtwo 10 ohm resistors. While this example shows specific circuit elementswith specific values, various other elements may be included. The outputstage 135 includes a 250 Ohm load with 2 nF capacitance.

FIG. 20B is an example of an output waveform produced from the portionof a pulse generator shown in FIG. 20A. The input waveform may include alow voltage (e.g., less than 200 V) input square waveform that may beprovided via V_(CH) and/or the driver stage 105. The input squarewaveform in this example was square wave with 5 μs pulse widths such as,for example, the waveform shown in FIG. 24A. As shown, the outputwaveform has an approximately 2 μs rise time and/or a very clean pulse.

FIG. 21A is an example circuit diagram 800 of a portion of a pulsegenerator according to some embodiments described in this document. Thecircuit diagram 800 shows a transformer stage 115 that includes a 1:5.5transformer. The circuit diagram 800 also shows a rectifier stage 120, afilter stage 125, and an output stage 135. The filter stage 125 in thisexample includes circuit elements that include two 480 μH inductors andtwo 10 ohm resistors. While this example shows specific circuit elementswith specific values, various other elements may be included. The outputstage 135 includes a 1 kOhm load with 470 pF capacitance.

FIG. 21B is an example of an output waveform produced from the pulsegenerator shown in FIG. 21A. The input waveform may include a lowvoltage (e.g., less than 200 V) input square waveform that may beprovided via V_(CH) and/or the driver stage 105. The input squarewaveform in this example was square wave with 5 μs pulse widths such as,for example, the waveform shown in FIG. 24A. As shown, the outputwaveform has an approximately 2 μs rise time and/or a relatively cleanpulse.

FIG. 22A is an example circuit diagram 900 of a portion of a pulsegenerator according to some embodiments described in this document. Thecircuit diagram 900 shows a transformer stage 115 that includes a 1:5.5transformer. The circuit diagram 900 also shows a rectifier stage 120and an output stage 135, but no filter stage 125. The output stage 135includes a 250 Ohm load.

FIG. 22B is an example of an output waveform produced from the pulsegenerator shown in FIG. 22A compared with the input waveform. A 200 Vinput square wave (dashed) was provided via V_(CH). As shown, the outputwaveform (solid) has a very sharp rise time and maintains a relativelyclean flat top with some slight ripple.

FIG. 22C is an example of an output waveform produced from the pulsegenerator shown in FIG. 22A compared with the input waveform into thetransformer stage 115. The input waveform may include a low voltage(e.g., less than 200 V) input square waveform that may be provided viaV_(CH). As shown, the output waveform has a very sharp rise time andmaintains a relatively clean flat top with some slight ripple.

FIG. 23A is an example circuit diagram 1,000 of a portion of a pulsegenerator according to some embodiments described in this document. Thecircuit diagram 1,000 shows a transformer stage 115 that includes a1:5.5 transformer. The circuit diagram 1,000 also shows a rectifierstage 120, a filter stage 125, and an output stage 135. The filter stage125 in this example includes circuit elements that include two 450 μHinductors. While this example shows specific circuit elements withspecific values, various other elements may be included. The outputstage 135 includes a 250 Ohm load.

FIG. 23B is an example of an output waveform produced from the pulsegenerator shown in FIG. 23A compared with the input waveform. A 200 Vinput square wave (dashed) was provided via V_(CH). As shown, the outputwaveform (solid) has a sharp rise time and maintains a clean flat topwith some slight ripple.

FIG. 23C is an example of an output waveform produced from the pulsegenerator shown in FIG. 23A compared with the input waveform. A 200 Vinput wave (dashed) with an arbitrary shape was provided via V_(CH). Asshown, the output waveform has a very sharp rise time and maintains arelatively clean flat top with some slight ripple.

FIG. 24A is an example circuit diagram 1100 of a portion of a pulsegenerator according to some embodiments described in this document. Thecircuit diagram 1100 shows a transformer stage 115 that includes a 1:5.5transformer. The circuit diagram 1100 also shows a rectifier stage 120,a filter stage 125, and an output stage 135. The filter stage 125 inthis example includes circuit elements that include two 125 μH inductorsand two 10 ohm resistors. While this example shows specific circuitelements with specific values, various other elements may be included.The output stage 135 includes a 250 Ohm load with 2 nF capacitance.

FIG. 24B is an example of an output waveform produced from the pulsegenerator shown in FIG. 24A compared with the input waveform. A 200 Vinput square wave (dashed) was provided via V_(CH). As shown, the outputwaveform (solid) has a sharp rise time and maintains a clean flat topwith very little ripple.

FIG. 24C is an example of an output waveform produced from the pulsegenerator shown in FIG. 24A compared with the input waveform with theload resistor, R_(L), replaced with a 1 kOhm resistor. In this example,the output waveform is substantially similar yet with the waveform inFIG. 24B but with a higher overshoot and with more ringing.

FIG. 25A is an example circuit diagram 1200 of a portion of a pulsegenerator according to some embodiments described in this document. Thecircuit diagram 1200 shows a transformer stage 115 that includes a 1:5.5transformer. The circuit diagram 1200 also shows a rectifier stage 120,a filter stage 125, and an output stage 135. The filter stage 125 inthis example includes circuit elements that include a single 125 μHinductor and a single 10 ohm resistor. While this example shows specificcircuit elements with specific values, various other elements may beincluded. The output stage 135 includes a 250 Ohm load with 2 nFcapacitance.

FIG. 25B is an example of an output waveform produced from the pulsegenerator shown in FIG. 25A compared with the output waveform producedfrom the pulse generator shown in FIG. 24A. The removal of one inductorand one resistor can provide for a faster rise time and/or a higheroutput voltage.

Some embodiments include a pulse generator that produces a square wavewith one or more of the following waveform specifications: a frequencyrange of 0.1 Hz to 10 MHz, a pulse width range of 10 ns to 10 μs, a risetime (and/or a fall time) of 1 ns to 100 μs, a duty cycle between 0 and100%, a flat top ripple range between 0 and 200%, and an output voltageof more than 1 kV, 2 kV, 5 kV, 10 kV, 30 kV, 100 kV, 300 kV, 1,000 kV.

Embodiments described within this document may include a pulse generatorthat produces an arbitrary and/or variable waveform with one or more ofthe following waveform specifications: a frequency range of 0.1 Hz to 10MHz, a pulse width range of 10 ns to 10 μs, a rise time and/or a falltime of 1 ns to 100 μs, a duty cycle between 0 and 100%, a dI/dt between10 A/s to 1,000 kA/μs and an output voltage of more than 1 kV, 2 kV, 5kV, 10 kV, 30 kV, 100 kV, 300 kV, 1,000 kV.

Embodiments described within this document may include a pulse generatorthat produces both high frequency pulses (e.g., pulses with a frequencygreater than 10 kHz) and low frequency pulses (e.g., pulses with afrequency less than 1 Hz or a DC pulse). Such a pulse generator may alsooutput voltages above 2 kV.

Embodiments described within this document may include a pulse generatorthat produces a high voltage DC pulse with a rise time of less than 10μs (or a rise time less than 1 μs), an output voltage greater than 1 kV,and/or a ripple between 2% and 50%.

FIG. 26A is an example circuit diagram 1300 of a portion of a pulsegenerator according to some embodiments described in this document. Thecircuit diagram 1300 shows a transformer stage 115 that includes a 1:5.5transformer. The circuit diagram 1300 also shows a rectifier stage 120and an output stage 135, but no filter stage 125. The output stage 135includes a 250 Ohm load.

FIG. 26B is an example of an output waveform compared with the inputwaveform. A 50 V input square wave (dashed) was provided via V_(CH). Asshown, the output waveform (solid) has a very sharp rise time (e.g.,about 50 ns) and has a high duty cycle (e.g., about 70%). Various otherduty cycles may be used such as, for example, duty cycles of anypercentage between 0% and 100%. In some embodiments, the duty cycle maychange over time.

FIG. 27A is an example circuit diagram 1400 of a portion of a pulsegenerator according to some embodiments described in this document. Thecircuit diagram 1400 shows a transformer stage 115 that includes a 1:5.5transformer. The circuit diagram 1400 also shows a rectifier stage 120and an output stage 145, but no filter stage 125. The output stage 145includes a 250 Ohm load.

FIG. 27B is an example of an output triangular wave waveform comparedwith the square wave input waveform. A 200 V input square wave (dashed)was provided via V_(CH). As shown, the triangular wave output waveform(solid) has a gradual rise time (e.g., about 4 μs) and a gradual falltime, which creates the triangular wave shape. The output waveform hasan amplitude of 1,000 volts.

In some embodiments, a pulse generator may produce a plurality of pulsesat high frequency (e.g., greater than 2 kHz) and high voltage (e.g.,greater than 2 kV) for a period of time, pause for a period of time, andthen begin pulsing at another frequency or the same frequency and highvoltage for another period of time. The pulse generator may repeat thisprocess over and over again. In some embodiments, the frequency and/orvoltage of each set of pulses may vary.

In some embodiments, the various pulse generators described in thisdocument may generate high voltage pulses (greater than 2 kV), with fastrise times (e.g., less than 100 ns) as well as with long and/or variablepulse widths and/or variable duty cycles. Pulse generators often cannotgenerate pulses that are a combination of fast features (e.g., fast risetimes) and slow features (e.g., long pulses). Some embodiments describedin this document can combine fast features with slow features.

FIG. 28 is a flowchart of a process 1500 for producing an arbitrarypulse width output signal according to some embodiments described inthis document. Process 1500 begins at block 1505 where a first inputwaveform is generated that has a first input frequency, a first inputduration, and a first input voltage. In some embodiments, the firstinput waveform may be generated from the driver stage 105. For example,the first input waveform may have a voltage of 200 volts to 2,000 voltsand/or has a frequency greater than 10 kHz. The first duration mayinclude any period of time. In some embodiments, the first duration maybe longer than two periods of the first input frequency. In someembodiments, the first duration may be between 10 s and 10 seconds.

At block 1510 a first output waveform is generated from the first outputwaveform having at least one of a first output voltage, a fast risetime, and/or a pulse width substantially equal to the first inputduration. In some embodiments, the first output voltage may be directlyproportional with the first input voltage. In some embodiments, thefirst output voltage may be greater than 2 kV. In some embodiments, thefast rise time may include a rise time less than about 5 μs or less thanabout 100 ns. Various other fast rise times and/or output voltages maybe used.

At block 1515 the first input waveform may be turned off for a secondinput duration. The first input waveform may be considered turned offwhen the waveform produces zero volts or a voltage at a DC bias voltagelevel. The second input duration, for example, may include any period oftime. For example, the second input duration may be longer than the risetime and/or the first input duration. As another example, the secondinput duration may be less than one period of the first input frequency.The second input duration may include any period of time.

At block 1520, at least one of the first input frequency, the firstinput duration, the first input voltage, and the second input durationmay be modified so a subsequent pulse may have a different outputvoltage, a different output duration, and/or a different period of timewhen the pulse produces zero volts or a voltage at a DC bias level.

After block 1520, the process 1500 may be repeated any number of timeswithout limitation. In some embodiments, during at least one cycle ofprocess 1500 none of the first input duration, the first input voltage,and the second input duration may be modified in block 1520.

The fast switching found in the driver stage 105 and the low inductancein various stages of a pulse generator may allow for fast rise timesand/or variable pulse widths. Embodiments described within this documentmay also produce, for example, high voltage pulses with variable dutycycle and/or variable frequency.

In some embodiments, more than one pulse generator may be combined inany combination such as, for example, in serial and/or in parallel. Insome embodiments, two pulse generators may be used with oppositepolarities and configured substantially identically to create a squarewave.

The term “substantially” and/or “about” means within 10% or 20% of thevalue referred to or within manufacturing tolerances.

Numerous specific details are set forth herein to provide a thoroughunderstanding of the claimed subject matter. However, those skilled inthe art will understand that the claimed subject matter may be practicedwithout these specific details. In other instances, methods,apparatuses, or systems that would be known by one of ordinary skillhave not been described in detail so as not to obscure claimed subjectmatter.

The use of “adapted to” or “configured to” herein is meant as open andinclusive language that does not foreclose devices adapted to orconfigured to perform additional tasks or steps. Additionally, the useof “based on” is meant to be open and inclusive, in that a process,step, calculation, or other action “based on” one or more recitedconditions or values may, in practice, be based on additional conditionsor values beyond those recited. Headings, lists, and numbering includedherein are for ease of explanation only and are not meant to belimiting.

While the present subject matter has been described in detail withrespect to specific embodiments thereof, it will be appreciated thatthose skilled in the art, upon attaining an understanding of theforegoing, may readily produce alterations to, variations of, andequivalents to such embodiments. Accordingly, it should be understoodthat the present disclosure has been presented for-purposes of examplerather than limitation, and does not preclude inclusion of suchmodifications, variations, and/or additions to the present subjectmatter as would be readily apparent to one of ordinary skill in the art.

That which is claimed:
 1. A high voltage, high frequency switchingcircuit comprising: a high voltage switching power supply that producespulses having a voltage greater than 1 kV and with frequencies greaterthan 10 kHz; an output; and a resistive output stage electricallycoupled to, and in parallel with the output of the high voltageswitching power supply, the resistive output stage comprising at leastone resistor that discharges a load coupled with the output, theresistive output stage configured to dissipate over about 1 kilowatt ofaverage power.
 2. The high voltage, high frequency switching circuitaccording to claim 1, wherein the high voltage switching power supplycomprises a power supply, at least one switch, and a step-uptransformer.
 3. The high voltage, high frequency switching circuitaccording to claim 1, wherein the output is coupled with a plasma loadthat is largely capacitive.
 4. The high voltage, high frequencyswitching circuit according to claim 1, wherein the output is coupledwith a plasma load that includes a dielectric barrier discharge.
 5. Thehigh voltage, high frequency switching circuit according to claim 1,wherein the resistance of the resistor in the resistive output stage hasa value less than about 400 ohms.
 6. The high voltage, high frequencyswitching circuit according to claim 1, wherein the high voltage highfrequency switching power supply delivers peak powers greater than 100kW.
 7. The high voltage, high frequency switching circuit according toclaim 1, wherein the resistor in the resistive output stage includes aresistance R and the output is coupled with a load having a capacitanceC such that R≈C/t_(f) where t_(f) is the pulse fall time.
 8. The highvoltage, high frequency switching circuit according to claim 1, whereinthe load is capacitive in nature with a capacitance less than 50 nF,wherein the load capacitance does not hold charges for times greaterthan 10 μs.
 9. The high voltage, high frequency switching circuitaccording to claim 1, wherein the load is capacitive in nature and thehigh voltage, high frequency switching circuit rapidly charges the loadcapacitance and discharges the load capacitance.
 10. The high voltage,high frequency switching circuit according to claim 1, wherein theoutput produces a negative bias voltage within a plasma of greater than−2 kV when the high voltage switching power supply is not providing ahigh voltage pulse.
 11. The high voltage, high frequency switchingcircuit according to claim 1, wherein the output can produce a highvoltage pulse having a voltage greater than 1 kV and with frequenciesgreater than 10 kHz with pulse fall times less than about 400 ns. 12.The high voltage, high frequency switching circuit according to claim 1,wherein the resistive output stage comprises at least one inductor inseries with the at least one resistor.
 13. A high voltage, highfrequency switching circuit comprising: a high voltage switching powersupply that produces pulses having a voltage greater than 1 kV and withfrequencies greater than 10 kHz; an output; and a resistive output stageelectrically coupled to, and in parallel with the output of the highvoltage switching power supply, the resistive output stage comprising atleast one resistor that discharges a load coupled with the output,wherein the output can produce a high voltage pulse having a voltagegreater than 1 kV and with frequencies greater than 10 kHz and with apulse fall time less than about 400 ns.
 14. The high voltage, highfrequency switching circuit according to claim 13, wherein the resistiveoutput stage comprises at least one inductor in series with the at leastone resistor.
 15. The high voltage, high frequency switching circuitaccording to claim 13, wherein the resistive output stage handles a peakpower greater than 10 kW.
 16. The high voltage, high frequency switchingcircuit according to claim 13, wherein the resistance of the resistor inthe resistive output stage is less than about 400 ohms.
 17. The highvoltage, high frequency switching circuit according to claim 13, whereinthe high voltage switching power supply establishes a potential within aplasma that is used to accelerate ions into a surface.
 18. The highvoltage, high frequency switching circuit according to claim 13, whereinthe output produces a negative bias voltage within a plasma of greaterthan −2 kV when the high voltage switching power supply is not providinga high voltage pulse.
 19. A high voltage, high frequency switchingcircuit comprising: a high voltage switching power supply that producespulses having a voltage greater than 1 kV and with frequencies greaterthan 10 kHz; an output; and a resistive output stage electricallycoupled to, and in parallel with the output of the high voltageswitching power supply, the resistive output stage comprising at leastone resistor, wherein the output can produce a high voltage pulse havinga voltage greater than 1 kV with frequencies greater than 10 kHz andwith pulse fall times less than about 400 ns, and wherein the output iselectrically coupled to a plasma type load.
 20. The high voltage, highfrequency switching circuit according to claim 19, wherein the resistiveoutput stage comprises at least one inductor in series with the at leastone resistor.
 21. The high voltage, high frequency switching circuitaccording to claim 19, wherein the plasma type load can be modeled ashaving capacitive elements less than 20 nF in size.
 22. The highvoltage, high frequency switching circuit according to claim 19, whereinthe plasma type load is designed to accelerate ions in the plasma typeload into a surface.
 23. The high voltage, high frequency switchingcircuit according to claim 19, wherein the high voltage high frequencyswitching power supply delivers peak powers greater than 100 kW.
 24. Thehigh voltage, high frequency switching circuit according to claim 19,wherein the high voltage switching power supply comprises a powersupply, at least one switch, and a step-up transformer.